Question 1

Figure 13.1.1
For the two-stage CMOS op amp shown in Fig. 13.1.1, all transistors have the same channel length $L=0.8 \mu \mathrm{m}, V_{t n}=-V_{t p}=0.6 \mathrm{~V}, \mu_{n} C_{o x}=$ $2 \mu_{p} C_{o x}=200 \mu \mathrm{A} / \mathrm{V}^{2}$, and $\left|V_{A}\right|=20 \mathrm{~V}$. Transistors $Q_{5}, Q_{7}$, and $Q_{8}$ are matched; $Q_{1}$ and $Q_{2}$ are matched; and $Q_{3}$ and $Q_{4}$ are matched.
Parts (a) to (d) below deal with de bias calculations, and in these, assume the two input terminals are grounded and neglect the Early effect.
(a) Find the values of $R, W_{8}, W_{5}$, and $W_{7}$ so that a dc voltage of $-1.5 \mathrm{~V}$ appears at the gate of $Q_{5}$ and dc current of $50 \mu \mathrm{A}$ flows in the drains of $Q_{1}$ and $Q_{2}$.
(b) Find $W_{1}$ and $W_{2}$ that will result in each of $Q_{1}$ and $Q_{2}$ operating with an overdrive voltage of $0.2 \mathrm{~V}$.
(c) Find $W_{3}$ and $W_{4}$ that will result in a dc voltage of $+1.5 \mathrm{~V}$ at the gates of $Q_{3}$ and $Q_{4}$.
(d) What de voltage appears at the gate of $Q_{6}$ ? Find $W_{6}$ that will result in zero de current flowing through the output terminal of the amplifier. 
(e) Find the input common-mode range.
(f) Find the allowable range of the output signal swing.
(g) Find the values of $g_{m 1}, g_{m 2}, r_{o 2}$, and $r_{o 4}$.
(h) Find the value of the differential gain of the first stage, $A_{1}=v_{o 1} / v_{i d}$.
(i) Recalling that the common-mode gain of the current-mirror-loaded differential amplifier is given by $\left(-1 / 2 g_{m 3} R_{S S}\right)$, where $R_{S S}$ is the output resistance of $Q_{5}$, find $g_{m 3}, R_{S S}$, the commonmode gain, and the CMRR in $\mathrm{dB}$.
(j) Find $g_{m 6}, r_{o 6}$, and $r_{o 7}$.
(k) Find the voltage gain of the second stage, $A_{2}=$ $v_{0} / v_{01}$.
(1) Find the overall differential voltage gain $v_{O} / v_{i d}$ and the output resistance $R_{O}$.
(m) If the feedback loop around the amplifier is closed by connecting the output terminal to the inverting input terminal, find the closedloop gain $A_{f}$ (between the non-inverting input terminal and the output) specified to four significant digits and determine the closed-loop output resistance $R_{o f}$.
(n) If, alternatively, the feedback loop around the op amp is closed by connecting the feedback network shown in Fig. 13.1.2, find the new values of $A$ and $R_{O}$ and the values of $\beta$, the closed-loop gain $A_{f}$, and the output resistance $R_{o f}$.

Figure 13.1.2

Accepted Answer

Figure 13.1.1
(a) With $V_{G 8}=V_{G 7}=V_{G 5}=-1.5 \mathrm{~V}$,
$$V_{G S 5}=V_{G S 7}=V_{G S 8}=1 \mathrm{~V}$$
Thus, each of $Q_{5}, Q_{7}$, and $Q_{8}$ is operating at
$$V_{O V}=1-0.6=0.4 \mathrm{~V}$$
To obtain $I_{D 1}=I_{D 2}=50 \mu \mathrm{A}$, we must establish
$$I_{D 5}=100 \mu \mathrm{A}$$
Thus,
$$I_{\mathrm{REF}}=I_{D 8}=I_{D 5}=100 \mu \mathrm{A}$$
But
$$\begin{aligned}
I_{\mathrm{REF}} & =\frac{V_{D D}-V_{G 8}}{R} \
0.1
 & =\frac{2.5-(-1.5)}{R} \
\Rightarrow R & =40 \mathrm{k} \Omega
\end{aligned}$$
For each of $Q_{5}, Q_{7}$, and $Q_{8}$,
$$\begin{aligned}
I_{D} & =\frac{1}{2}\left(\mu_{n} C_{O x}\right)\left(\frac{W}{L}\right) V_{O V}^{2} \
100 & =\frac{1}{2} \times 200 \times\left(\frac{W}{L}\right) \times 0.4^{2} \
\Rightarrow \frac{W}{L} & =6.25
\end{aligned}$$
Thus, $W_{5}=W_{7}=W_{8}=6.25 \times 0.8=5 \mu \mathrm{m}$.
(b) For each of $Q_{1}$ and $Q_{2}$,
$$\begin{aligned}
I_{D} & =\frac{1}{2}\left(\mu_{n} C_{O x}\right)\left(\frac{W_{1,2}}{L}\right) V_{O V 1,2}^{2} \
50 & =\frac{1}{2} \times 200 \times \frac{W_{1,2}}{L} \times 0.2^{2} \
\Rightarrow \frac{W_{1,2}}{L} & =12.5 \
\Rightarrow W_{1} & =W_{2}=12.5 \times 0.8=10 \mu \mathrm{m}
\end{aligned}$$
(c)
$$\begin{aligned}
V_{G 3}=V_{G 4} & =+1.5 \mathrm{~V} \
\Rightarrow V_{S G 3}=V_{S G 4} & =1 \mathrm{~V} \
\Rightarrow\left|V_{O V 3,4}\right| & =0.4 \mathrm{~V}
\end{aligned}$$
For $Q_{3}$ and $Q_{4}$,
$$\begin{aligned}
I_{D} & =\frac{1}{2}\left(\mu_{p} C_{O x}\right)\left(\frac{W_{3,4}}{L}\right)\left|V_{O V 3,4}\right|^{2} \
50 & =\frac{1}{2} \times 100 \times \frac{W_{3,4}}{L} \times 0.4^{2} \
\Rightarrow \frac{W_{3,4}}{L} & =6.25 \mu \mathrm{m} \
\Rightarrow W_{3} & =W_{4}=6.25 \times 0.8=5 \mu \mathrm{m}
\end{aligned}$$
(d) For matched conditions,
$$\begin{aligned}
V_{D 4} & =V_{G 4}=+1.5 \mathrm{~V} \
\Rightarrow V_{G 6} & =+1.5 \mathrm{~V} \
V_{S G 6} & =1 \mathrm{~V}
\end{aligned}$$
Thus, $Q_{6}$ will be operating at $\left|V_{O V}\right|=0.4 \mathrm{~V}$. For zero dc output current,
$$I_{D 6}=I_{D 7}=100 \mu \mathrm{A}$$
Thus,
$$\begin{aligned}
100 & =\frac{1}{2}\left(\mu_{p} C_{o x}\right)\left(\frac{W_{6}}{L}\right)\left|V_{O V 6}\right|^{2} \
100 & =\frac{1}{2} \times 100 \times \frac{W_{6}}{L} \times 0.4^{2} \
\Rightarrow \frac{W_{6}}{L} & =12.5 \
\Rightarrow W_{6} & =12.5 \times 0.8=10 \mu \mathrm{m}
\end{aligned}$$
(e)
$$\begin{aligned}
V_{I C M \max } & =V_{D 1}+V_{t n}=+1.5+0.6=+2.1 \mathrm{~V} \
V_{I C M \min } & =-V_{S S}+V_{O V 5}+V_{G S 1} \
& =-2.5+0.4+(0.6+0.2)=-1.3 \mathrm{~V}
\end{aligned}$$
Thus,
$$-1.3 \mathrm{~V} \leq V_{I C M} \leq+2.1 \mathrm{~V}$$
(f)
$$\begin{aligned}
v_{O \max } & =V_{D D}-\left|V_{O V 6}\right| \
& =+2.5-0.4=+2.1 \mathrm{~V} \
v_{O \min } & =-V_{S S}+V_{O V 7} \
& =-2.5+0.4=-2.1 \mathrm{~V}
\end{aligned}$$
Thus,
$$-2.1 \mathrm{~V} \leq v_{O} \leq+2.1 \mathrm{~V}$$
(g)
$$\begin{aligned}
g_{m 1} & =g_{m 2}=\frac{2 I_{D 1,2}}{V_{O V 1,2}} \
& =\frac{2 \times 0.05}{0.2}=0.5 \mathrm{~mA} / \mathrm{V} \
r_{o 2} & =\frac{V_{A}}{I_{D 2}}=\frac{20 \mathrm{~V}}{50 \mu \mathrm{A}}=400 \mathrm{k} \Omega \
r_{o 4} & =\frac{\left|V_{A}\right|}{I_{D 4}}=\frac{20 \mathrm{~V}}{50 \mu \mathrm{A}}=400 \mathrm{k} \Omega
\end{aligned}$$
(h)
$$\begin{aligned}
A_{1} & \equiv \frac{v_{o 1}}{v_{i d}}=g_{m 1,2}\left(r_{o 2} \| r_{o 4}\right) \
& =0.5 \times(400 \| 400)=100 \mathrm{~V} / \mathrm{V}
\end{aligned}$$
(i)
$$\begin{aligned}
g_{m 3} & =\frac{2 I_{D 3}}{\left|V_{O V 3}\right|}=\frac{2 \times 0.05}{0.4}=0.25 \mathrm{~mA} / \mathrm{V} \
R_{S S} & =\frac{V_{A}}{I_{D 5}}=\frac{20}{0.1}=200 \mathrm{k} \Omega \
A_{c m} & =-\frac{1}{2 g_{m 3} R_{S S}} \
& =-\frac{1}{2 \times 0.25 \times 200}=-0.01 \mathrm{~V} / \mathrm{V} \
\mathrm{CMRR} & =\frac{\left|A_{d 1}\right|}{\left|A_{c m}\right|}=\frac{100}{0.01}=10^{4}
\end{aligned}$$
or $80 \mathrm{~dB}$.
(j)
$$\begin{gathered}
g_{m 6}=\frac{2 I_{D 6}}{\left|V_{O V 6}\right|}=\frac{2 \times 0.1}{0.4}=0.5 \mathrm{~mA} / \mathrm{V} \
r_{o 6}=r_{o 7}=\frac{\left|V_{A}\right|}{I_{D 6,7}}=\frac{20}{0.1}=200 \mathrm{k} \Omega
\end{gathered}$$
(k)
$$\begin{aligned}
A_{2} & =\frac{v_{o}}{v_{o 1}}=-g_{m 6}\left(r_{o 6} \| r_{o 7}\right) \
& =-0.5(200 \| 200)=-50 \mathrm{~V} / \mathrm{V}
\end{aligned}$$
(1)
$$\begin{aligned}
& \frac{v_{o}}{v_{i d}}=A_{1} A_{2}=100 \times-50=-5000 \mathrm{~V} / \mathrm{V} \
& R_{o}=r_{o 6}\left\|r_{o 7}=200\right\| 200=100 \mathrm{k} \Omega
\end{aligned}$$
(m)

$$A_{f}=\frac{A}{1+A \beta}$$
where $A=5000$ and $\beta=1$. Thus,
$$\begin{aligned}
A_{f} & =\frac{5000}{5001}=0.9998 \mathrm{~V} / \mathrm{V} \
R_{o f} & =\frac{R_{o}}{1+A \beta} \
& =\frac{100 \mathrm{k} \Omega}{5001}=20 \Omega
\end{aligned}$$
(n)

Figure 13.1.4
  
Figure 13.1.5

Figure 13.1.6
The feedback amplifier is shown in Fig. 13.1.4, the $\beta$ network in Fig. 13.1.5, and the $A$ circuit in Fig. 13.1.6. The gain $A$ becomes
$$A=A_{1} A_{2}^{\prime}$$
where
$$A_{1}=100 \mathrm{~V} / \mathrm{V}$$
and
$$\begin{aligned}
A_{2}^{\prime} & =g_{m 6}\left[r_{o 6}\left\|r_{o 7}\right\|(90+10)\right] \
& =0.5[200\|200\| 100] \
A_{2}^{\prime} & =25 \mathrm{~V} / \mathrm{V}
\end{aligned}$$
Thus,
$$\begin{aligned}
A & =100 \times 25=2500 \mathrm{~V} / \mathrm{V} \
\beta & =\frac{10}{90+10}=0.1 \
A_{f} & \equiv \frac{V_{o}}{V_{S}}=\frac{A}{1+A \beta} \
& =\frac{2500}{1+2500 \times 0.1}=\frac{2500}{251} \
& =9.96 \mathrm{~V} / \mathrm{V} \
R_{O} & =r_{o 6}\left\|r_{o}\right\|(90+10) \
& =200\|200\| 100=50 \mathrm{k} \Omega \
R_{o f} & =\frac{R_{O}}{1+A \beta}=\frac{50 \mathrm{k} \Omega}{251} \simeq 200 \Omega
\end{aligned}$$

Question 2

Figure 13.2.1
It is required to design the folded-cascode op amp shown in Fig. 13.2.1. Let $V_{D D}=V_{S S}=1 \mathrm{~V}$ and $V_{t n}=-V_{t p}=0.4 \mathrm{~V}$, and assume that for all transistors, $\left|V_{A}\right|=6 \mathrm{~V}$. Design so that the power dissipated in the circuit (with no input signal applied) is $0.6 \mathrm{~mW}$, and so that each of $Q_{1}$ and $Q_{2}$ is operating at a current four times that at which each of $Q_{3}$ and $Q_{4}$ is operating. Also, design so that all transistors operate at $\left|V_{O V}\right|=0.2 \mathrm{~V}$.
(a) Show that the current drawn from each of the two power supplies is $2 I_{B}$, and hence find $I_{B}$ and $I$ that result in the circuit operating at its specified power dissipation.
(b) Find the dc current at which each of $Q_{1}$ to $Q_{11}$ is operating. Present your results in a table.
(c) Find the input common-mode range. 
(d) Find the required values of $V_{\mathrm{BIAS} 1}, V_{\mathrm{BIAS} 2}$, and $V_{\mathrm{BIAS} 3}$ that result in the maximum allowable value of $v_{O}$ to be as high as possible.
(e) Find the allowable range of $v_{O}$.
(f) Find the overall transconductance $G_{m}$.
(g) Find the output resistance $R_{O}$.
(h) Find the low-frequency voltage gain.
(i) If the amplifier at its output is modeled by a controlled current-source $G_{m} V_{i d}$ (where $V_{i d}$ is the differential input voltage) feeding the output resistance $R_{O}$ and the total capacitance at the output node $C_{L}$, find the value of $C_{L}$ that results in the amplifier having a unity-gain bandwidth of $100 \mathrm{MHz}$. Assume that the dominant pole is that formed at the output.

Accepted Answer

Figure 13.2.1
(a)
$$I_{D D}=I_{D 9}+I_{D 10}=2 I_{B}$$
Since each of $Q_{1}$ and $Q_{2}$ is conducting a current $I / 2$, we can see from node equations at $D_{1}$ and $D_{2}$ that
$$I_{D 3}=I_{D 4}=I_{B}-\frac{I}{2}$$
Now,
$$\begin{aligned}
I_{S S} & =I_{D 11}+I_{D 7}+I_{D 8} \
& =I+\left(I_{B}-\frac{I}{2}\right)+\left(I_{B}-\frac{I}{2}\right) \
& =2 I_{B} \quad \text { Q.E.D } \
P_{D} & =V_{D D} \times 2 I_{B}+V_{S S} \times 2 I_{B} \
& =1 \times 2 I_{B}+1 \times 2 I_{B}=4 I_{B}
\end{aligned}$$
For $P_{D}=0.6 \mathrm{~mW}$,
$$I_{B}=\frac{0.6}{4}=0.15 \mathrm{~mA}=150 \mu \mathrm{A}$$
For $I_{D 1,2}=4 I_{D 3,4}$,
$$\begin{aligned}
\frac{I}{2} & =4\left(I_{B}-\frac{I}{2}\right) \
\Rightarrow I & =\frac{4 I_{B}}{2.5}=\frac{600}{2.5}=240 \mu \mathrm{A}
\end{aligned}$$
(b)

(c)
$$\begin{aligned}
V_{I C M \max } & =V_{D 1 \max }+V_{t n} \
& =V_{D D}-\left|V_{O V 9}\right|+V_{t n} \
& =+1-0.2+0.4=+1.2 \mathrm{~V} \
V_{I C M \min } & =-V_{S S}+V_{O V 11}+V_{G S 1} \
& =-1+0.2+(0.4+0.2)=-0.2 \mathrm{~V}
\end{aligned}$$
Thus,
$$-0.2 \mathrm{~V} \leq V_{I C M} \leq+1.2 \mathrm{~V}$$
(d) To make $v_{O \max }$ as high as possible,
$$\begin{aligned}
V_{\mathrm{BIAS} 1} & =V_{D D}-\left|V_{O V 9,10}\right|-V_{S G 3,4} \
& =+1-0.2-(0.4+0.2)=+0.2 \mathrm{~V} \
V_{\mathrm{BIAS} 2} & =V_{D D}-V_{S G 9,10} \
& =+1-(0.4+0.2)=+0.4 \mathrm{~V} \
V_{\mathrm{BIAS} 3} & =-V_{S S}+V_{G S 11} \
& =-1+(0.4+0.2)=-0.4 \mathrm{~V}
\end{aligned}$$
(e)
$$\begin{aligned}
v_{O \max } & =V_{\mathrm{BIAS} 1}+\left|V_{t p}\right| \
& =0.2+0.4=+0.6 \mathrm{~V} \
v_{O \min } & =-V_{S S}+V_{G S 7}+V_{G S 5}-V_{t n} \
& =-1+(0.4+0.2)+(0.4+0.2)-0.4 \
& =-0.2 \mathrm{~V}
\end{aligned}$$
Thus,
$$-0.2 \mathrm{~V} \leq v_{O} \leq+0.6 \mathrm{~V}$$
(f)
$$\begin{aligned}
G_{m} & =g_{m 1,2}=\frac{2 I_{D 1,2}}{V_{O V}} \
& =\frac{2 \times 0.12}{0.2}=1.2 \mathrm{~mA} / \mathrm{V}
\end{aligned}$$
(g)
$$\begin{aligned}
R_{O} & =R_{O 4} \| R_{o 6} \
R_{o 4} & =\left(g_{m 4} r_{o 4}\right)\left[r_{o 10} \| r_{o 2}\right] \
r_{o 10} & =\frac{\left|V_{A}\right|}{I_{B}}=\frac{6}{0.15}=40 \mathrm{k} \Omega \
r_{o 2} & =\frac{V_{A}}{I_{D 2}}=\frac{6}{0.12}=50 \mathrm{k} \Omega \
g_{m 4} & =\frac{2 I_{D 4}}{\left|V_{O V}\right|}=\frac{2 \times 0.03}{0.2}=0.3 \mathrm{~mA} / \mathrm{V} \
r_{o 4} & =\frac{\left|V_{A}\right|}{I_{D 4}}=\frac{6}{0.03}=200 \mathrm{k} \Omega \
g_{m 4} r_{o 4} & =0.3 \times 200=60 \
R_{o 4} & =60(40 \| 50) \
& =1.33 \mathrm{M} \Omega \
R_{o 6} & =\left(g_{m 6} r_{o 6}\right) r_{o 8} \
g_{m 6} & =\frac{2 I_{D 6}}{V_{O V}}=\frac{2 \times 0.03}{0.2}=0.3 \mathrm{~mA} / \mathrm{V} \
r_{o 6} & =\frac{V_{A}}{I_{D 6}}=\frac{6}{0.03}=200 \mathrm{k} \Omega
\end{aligned}$$
$$\begin{aligned}
r_{o 8} & =\frac{V_{A}}{I_{D 8}}=\frac{6}{0.03}=200 \mathrm{k} \Omega \
R_{o 6} & =(0.3 \times 200) \times 200=12 \mathrm{M} \Omega \
R_{O} & =R_{o 4}\left\|R_{o 6}=1.33\right\| 12 \
& =1.2 \mathrm{M} \Omega
\end{aligned}$$
(h)
$$\begin{aligned}
A_{v} & =G_{m} R_{O}=1.2 \times 1.2 \times 10^{3}=1.44 \times 10^{3} \
& =1440 \mathrm{~V} / \mathrm{V}
\end{aligned}$$
(i)
  
Figure 13.2.2
Figure 13.2.2 shows the output equivalent circuit of the amplifier. At high frequencies,
$$\begin{aligned}
& V_{o}=\frac{G_{m} V_{i d}}{s C_{L}} \
\left|\frac{V_{o}}{V_{i d}}\right|=1 \text { at } & \
& \omega=\omega_{t}=\frac{G_{m}}{C_{L}}
\end{aligned}$$
Thus,
$$\begin{aligned}
C_{L} & =\frac{G_{m}}{\omega_{t}} \
& =\frac{1.2 \times 10^{-3}}{2 \pi \times 100 \times 10^{6}}=1.9 \mathrm{pF}
\end{aligned}$$

Question 3

In the current-mirror circuits in Fig. 13.3.1, all transistors are operating at the same current and have the same $V_{O V}$ and the same $V_{A}$. Identify each current-mirror (i.e., give its name) and give its output resistance $R_{O}$ in terms of $I_{\mathrm{REF}}, V_{O V}$, and $V_{A}$. Also, give the minimum voltage $V_{O}$ each mirror requires to operate properly. Give $V_{O}$ in terms of $V_{t}$ and $V_{O V}$.

Accepted Answer

(a) Simple or basic current mirror.
$$\begin{aligned}
R_{O} & =r_{O 2}=\frac{V_{A}}{I_{O}}=\frac{V_{A}}{I_{\mathrm{REF}}} \
V_{O \min } & =V_{O V}
\end{aligned}$$
(b) Cascode current mirror.
$$R_{o}=\left(g_{m 4} r_{o 4}\right) r_{o 2}$$
where
$$\begin{aligned}
g_{m 4} & =\frac{2 I_{D}}{V_{O V}}=\frac{2 I_{\mathrm{REF}}}{V_{O V}} \
r_{o 2} & =r_{o 4}=\frac{V_{A}}{I_{D}}=\frac{V_{A}}{I_{\mathrm{REF}}}
\end{aligned}$$
Thus,
$$\begin{aligned}
R_{o} & =\left(\frac{2 V_{A}}{V_{O V}}\right)\left(\frac{V_{A}}{I_{\mathrm{REF}}}\right) \
V_{O \min } & =2 V_{G S}-V_{t}=V_{t}+2 V_{O V}
\end{aligned}$$
(c) Modified Wilson current mirror. $R_{O}$ is the same as that of the cascode mirror,
$$R_{O}=\left(\frac{2 V_{A}}{V_{O V}}\right)\left(\frac{V_{A}}{I_{\mathrm{REF}}}\right)$$
Also, $V_{O \min }$ is the same as that of the cascode mirror,
$$V_{O \text { min }}=V_{t}+2 V_{O V}$$
(d) Wide-swing current mirror. $R_{O}$ is the same as that of the cascode,
$$R_{O}=\left(\frac{2 V_{A}}{V_{O V}}\right)\left(\frac{V_{A}}{I_{\mathrm{REF}}}\right)$$
However, here $V_{O \min }$ is
$$\begin{aligned}
V_{O \min } & =V_{G 4}-V_{t} \
& =V_{t}+2 V_{O V}-V_{t}=2 V_{O V}
\end{aligned}$$

Question 4

Figure 14.1.1
It is required to design a fifth-order Butterworth low-pass filter with a de gain of unity, a passband edge of $10^{4} \mathrm{rad} / \mathrm{s}$, and a maximum deviation in the passband transmission of $3 \mathrm{~dB}$ (i.e., $\epsilon=1$ ).
(a) Find the transfer function $T(s)$ and give $\omega_{0}$ and $Q$ of each of the two pairs of complex-conjugate poles. Also, specify the frequency of the real pole.
 (b) Provide a complete circuit realization of the filter as a cascade of two second-order sections and a first-order section. For the second-order sections, use realizations based on the inductancesimulation circuit of Fig. 14.1.1. For the first-order section, use an op amp-RC circuit. Design so that all capacitors are equal to $10 \mathrm{nF}$ and as many of the resistors as possible are equal. Give the complete circuit and specify the values of all resistors.

(c) What is the attenuation achieved at the stopband edge, $2 \times 10^{4} \mathrm{rad} / \mathrm{s}$ ?

Accepted Answer

The answer of

Figure 14.1.1
It is required to design...

Question 5

In the cross-coupled oscillator circuit shown in Fig. 15.1.1, $R_{p}$ represents the loss of each inductor. Each transistor is operating at a transconductance $g_{m}$ and has an output resistance $r_{o}$. Find the oscillation frequency $\omega_{0}$ and explain why the circuit oscillates at this frequency. Also, derive an expression for the minimum value of $g_{m}$ needed to obtain sustained oscillations.

Figure 15.1.1

Accepted Answer

The answer of In the cross-coupled oscillator circuit shown in...

Question 6

Figure 16.1.1
(a) For the CMOS inverter in Fig. 16.1.1, $Q_{N}$ and $Q_{P}$ have $\left|V_{t}\right|=0.5 \mathrm{~V}$ and $k_{n}=k_{p}=1 \mathrm{~mA} / \mathrm{V}^{2}$. Sketch and clearly label the VTC $v_{O}$ versus $v_{I}$ and give values for the noise margins $N M_{L}$ and $N M_{H}$. What is the output resistance when $v_{O}=0 \mathrm{~V}$ ?
(b) Provide the CMOS realization of the logic function.
$$Y=\overline{A(B+C)+D}$$

Accepted Answer

The answer of

Figure 16.1.1
(a) For the CMOS inverter...

Question 7

The CMOS inverter shown in Fig. 16.2.1 has $V_{D D}=1.8 \mathrm{~V}$ and is fabricated in a $0.18-\mu \mathrm{m}$ process for which $\mu_{n}=4 \mu_{p}, \mu_{n} C_{o x}=400 \mu \mathrm{A} / \mathrm{V}^{2}$, and $V_{t n}=-V_{t p}=0.4 \mathrm{~V}$. For this problem, neglect the Early effect. Both $Q_{N}$ and $Q_{P}$ use the minimum channel length allowed. For $Q_{N}, W / L=1.5$.
(a) Find the dimensions that $Q_{P}$ must have in order for the inverter switching to occur at $v_{I}=0.9 \mathrm{~V}$.
(b) What are the noise margins of the inverter?
(c) What current flows in $Q_{N}$ and $Q_{P}$ at the switching point?
(d) For $v_{I}=1.8 \mathrm{~V}$, what is the maximum current that $Q_{N}$ can sink while $v_{O}$ is limited to $0.4 \mathrm{~V}$ ?

Accepted Answer

The answer of

The CMOS inverter shown in Fig....

Question 8

Figure 16.3.1
The CMOS inverter shown in Fig. 16.3.1 is fabricated in a $0.18-\mu \mathrm{m}$ technology having $\left|V_{t}\right|=0.4 \mathrm{~V}$, $k_{n}^{\prime}=0.4 \mathrm{~mA} / \mathrm{V}^{2}$, and $\mu_{p}=\frac{1}{3} \mu_{n}$.
(a) Find $W_{p}$ to obtain matched transistors.
(b) For $v_{I}=1.8 \mathrm{~V}$, find the maximum load current that the inverter can sink while $v_{O}$ is not exceeding $0.1 \mathrm{~V}$.

Accepted Answer

The answer of

Figure 16.3.1
The CMOS inverter shown in...

Question 9

Figure 16.4.1
The transistors in the CMOS inverter in Fig. 16.4.1 have $k_{n}^{\prime}(W / L)_{n}=k_{p}^{\prime}(W / L)_{p}=10 \mathrm{~mA} / \mathrm{V}^{2},\left|V_{t}\right|=$ $1 \mathrm{~V}$, and $\lambda=0$.
(a) What is the value of the gate threshold?
(b) For $v_{I}=0 \mathrm{~V}$, what is the resistance between the output terminal and the $V_{D D}$ supply? If a resistance $R_{L}=1 \mathrm{k} \Omega$ is connected between the output terminal and ground, what will $v_{O}$ be?

Accepted Answer

The answer of

Figure 16.4.1
The transistors in the CMOS...

Quiz 8: Operational Amplifier Circuits, Filters, Oscillators and CMOS Digital Logic Circuits